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(R)
TD230
ELECTRONIC CIRCUIT BREAKER
.TWON.DUALSUPPLYOPERATI .FROM+3/ .STEP.ADJUSTABLE .I .SHUTDOWNOUTPUTSTATUS .FEWEXTERNALCOMPONENTS
CHANNEL MOSFETs CONTROL AND DUAL INDEPENDANT CURRENT SUPERVISION FOR OVER CURRENT PROTECTION ON -5 TO +18/-18V OPERATING VOLTAGE UPCONVERTER : VCC +13.5V OUTPUT VOLTAGE P ROT ECTI O N MODE (CTRIP1/2) NHIBIT FUNCTION
N DIP16 (Plastic Package)
D SO16 (Plastic Micropackage)
ORDER CODES
Part Number Temperature Range -40 C, +125 C
o o
Package N * D *
DESCRIPTION The TD230 is designed to control two N-channel MOSFETs used as power switches in circuit breaking applications. Its current supervision and immediate action on the switches ensure high security for the boards and the supplies thus protected against short-circuit or over current. In case of short-circuit or over current detection,the TD230 immediately switches off the corresponding MOSFET, thus disconnecting the board from the supply. After several automatic restart attempts, a definitive shutdown of the circuit is done if the shortcircuit or over current persists over an externally adjustable time, until the TD230 is reset by temporary INHIBIT signal or temporary switching off of the power supply (hot disconnection/reconnection). If the board is disconnected from the positive supply by the TD230 it will automatically be disjoncted from the negative supply too. TD230 integrates an induction step-up converter that provides 13.5V above the positive rail to drive the high side MOSFET.
October 1998
TD230I
PIN CONNECTIONS
P Vcc
1
16 15 14 13 12 11 10 9
REF1 GC1 S ENSP INHIBIT SHUTDOWN SENS N GC2 REF2
LBOOS T 2 CBOOST 3 OS CGND 4 PM1 GND PM2 NVcc
5 6 7 8
TD230
BLOCK DIAGRAM
PVcc
STEP -UP
LBOOST
o sc CBOOS T OS C GND
R EF1
VSP 1
IP1
INHIBIT
S W1
GC1
PVcc P M1 S E NSP IP 2 S HUTDOWN VSP 3 IP3
VSP 2
G ND VSN3 IN3
P M2 IN2 S ENSN VSN2
P Vcc P Vcc
IN1 S W2 GC2
VSN1
R EF2
NVcc
ABSOLUTE MAXIMUM RATINGS
Symbol VCC
+
Parameter Positive Supply Voltage Negative Supply Voltage Input Voltage Input Voltage Input Voltage Operating Junction Temperature Operating Ambient Temperature Storage Temperature Range
Value +22 -22 7 7 7 -40 to 150 -40 to 125 -65 to 150
Unit V V V V V
o o o
VCC Inhibit Shutdown PM1/PM2 Tj Tamb Tstg
C C C
OPERATING CONDITIONS
Symbol VCC Supply Voltage Parameter Value +/-18 Unit V
INSTRUCTIONS FOR USE
Symbol Cbypass Parameter Bypass Capacitor (each supply) Value 1 Unit F
2/15
TD230
ELECTRICAL CHARACTERISTICS VCC = +/-5V, Tamb = 25oC, Lboost = 220H, Cboost = 100nF (unless otherwise specified)
Symbol SUPPLY VCC+
VCC + ICC
Parameter Positive Supply Voltage Negative Supply Voltage Positive Supply Current Charge Pump Inactivated Charge Pump Activated Lboost = 220H, C boost = 100nF
Min. 2.7 -18
Typ.
Max. 18 -4.5
Unit V V mA mA mA
1.8 2.3 -0.7
3 4 -1.5
ICC
-
Negative Supply Current Charge Pump Activated/Inactivated LOGIC INPUT (INHIBIT) High Input Voltage Low Input Voltage Propagation Delay GC1/2 (without load) LOGIC OUTPUT (SHUTDOWN-open drain) Low Output Voltage (2mA) High Output Current (6V) Shutdown Response Time (sens P/N shutdown without load) STEP-UP CONVERTER Step-Up Output Voltage Rise Time for Vboost (10 to 90%) Output Ripple Voltge INPUT COMPARATORS Threshold (PVCC - Ref1, NVCC - Ref2) Response Time (GC1/2 - without load) Inhibition Time (without load) VOLTAGE SOURCES 56 VCC +10
+
VIH VIL tp VOL IOH ts
2 0 0.5
6 0.8 2 0.8 1 8 VCC +13.4 250 0.15 63 2
+
V V s V nA s
15 VCC +15 800 0.6 71 3 300
+
Vboost tvboost Vrip Vi tre ti VSP2 VSN2 VSP3 VSN3 IP1, IN1 IP2, IN2 IP3, IN3 R on
V s V mV s ns V V
Threshold Sense Pos/Neg Threshold Protection Mode CURRENT SOURCES Soft Start Current Sources Protection Mode Current Sources (loading Ctrip 1/2) Protection Mode Current Sources (discharging Ctrip 1/2) SWITCHES On-Resistance of the switches SW1/SW2
0.7 VCC+/1.10
0.75 VCC+/1.20
0.8 VCC+/1.30
10 3 0.6
15 4 1
20 5 1.4
A A A
90
200
3/15
TD230
Figure 1 : DUAL ELECTRONIC CIRCUIT BREAKER APPLICATION
RS1
Vcc+
P Vcc REF1
LBOOST
1
LBO OS T GC1
16
NMos
2
CBO OS T S ENS P
15 14 13 12 11 10
CS S1
to BOARD
CBOOS T
3
OS CGND
4 5
CTRIP1
P M1
INHIBIT
CONTR OL
S HUTDO WN
6
CTRIP2 G ND
GND
SE NS N
from BOARD NMOS
7 8
Vcc-
P M2 NVcc
GC2 REF2
CS S2
9
RS2
Figure 2 :
SINGLE ELECTRONIC CIRCUIT BREAKER APPLICATION
RS 1
Vcc+
P Vcc REF1
LBOO ST
1 2
LBOO S T GC1
16
NMos
15
S ENS P
CS S 1
to BOARD
CBOOS T
3 4 5
CBOO S T
14 13 12 11 10 9
CONTROL
OS CGND
INHIBIT
P M1
S HUTDOWN
CTRIP1
6 7
GND
GND
S ENS N
P M2 NVcc
GC2 REF2
8
4/15
TD230
TIMING DIAGRAMS
P owe r Norma l Curre nt Norma l Function Norma l Curre nt Norma l Function OFF ON Circuit OFF Norma l Curre nt Norma l Function Inhibit HI LO OFF Norma l Curre nt Norma l Func tion
E vents
S hort Circuit Current Limitation
Short Circuit Curre nt Limitation
Sta tus
PVc c- Vre f (=Vrs)
Vi
S e ns P P Vc c -
GC1-S e ns P = Vgs 13.4V
~5V
P M1=Vctrip1 PVc c Vsp3
ts s # PVc c. Css Ip1
S hutdown tpm1 # (Ctrip1.Vsp3) IP2-IP3 ts HiZ
Inhibit
tp TTL
PVcc -Vref (=Vrs)
PVcc -Vref (=Vrs)
t < ti
ti
tre
toff # Ro n.Cs s
Vi
Vi
G C1 -Se ns P = Vgs 13.4V
G C1 -Se ns P = Vgs 1 3 .4V
~5V
~5V
5/15
TD230
APPLICATION NOTE ELECTRONIC CIRCUIT BREAKER
by R. LIOU
INTRODUCTION Over current and short circuit protection is a constant concern for today's engineers. More and more applications in different segments (Telecom, Automotive, Industrial, Computer...) require always improved reliability after delivery : maintenance costs are an ever more worrying source of expenses and customers' dissatisfaction. Alternatives for short circuit or over current protections are the fuses and the PTC (Positive Temperature Coefficient) resistors. The first are a cheap but destructive solution ; the second are tied to a time constant due to self heating which is often incompatible with the host equipment's requirements. In both cases, a coil can be added for an efficient limitation of current surges, to the detriment of weight and volume. None of these solutions is fully satisfactory for a reliable, immediate and non destructible short circuit and over current protection. 1. ELECTRONIC CIRCUIT BREAKER The electronic circuit breaker TD230 is the convenient solution for any industrial who wants at the same time : * immediate, efficient and resettable protection for his equipment * versatility regarding different applications * easy and quick design-in * low component count * low cost The electronic circuit breaker TD230 is to be used with a minimal amount of external and low cost components to drive one or two N-channel MOSFETs (in respectively single or dual supply applications) used as power switches between the DC power supplies and the equipments to be protected. The TD230 immediately reacts (3s max. without load) whenever an over current is detected by switching off the corresponding MOSFET. Several automatic restart attempts are made unless the fault persists over an externally adjustable amount
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of time after which the power MOSFET is definitively switched off, waiting for a reset. If the fault is detected on the positive supply, the definitive shutdown will also disconnect the negative power supply and set a warning low level on the Shutdown pin. If the fault is detected on the negative supply, the definitive shutdown will disconnect only the negative power supply,and let the positive part of the circuit undisturbed. The whole system can be reset in three ways : * by switching off the power supplies * by unplugging and re-plugging the card (live insertion) * by setting the INHIBIT pin active during a short time (allowing remote reset) 2. HOW TO USE THE TD230 ? The typical configuration of the TD230 - Electronic Circuit Breaker - in a dual supply topology is shown in figure 1. In this configuration, both NMOS 1/2 are used as power switches which connect the equipments to the power supplies, thus ensuring low voltage drop through the ON-resistances (Rdson) of NMOS 1/2. 2.1. Current Limitation When an over current condition (IOC ) is detected through the low ohmic shunt resistors RS 1/2 as given under equation (i) : * VRS 1/2 = IOC x RS > 63mV typ. (i) the gate of the corresponding MOSFET 1/2 is discharged immediately, thus disconnecting the board/equipment from the power supply. Note that the over current condition is given by the constant product IOC x RS = 63mV, which means that the IOC limit is directly given by the choice of the shunt resistors RS1/2 values. The TD230 automatically makes restart attempts by slowly recharging the gate of the MOSFET 1/2 with a 15A typ. current source ensuring thus slow ramp with the typical time constant before reconduction shown in equation (ii) : * tON = CISS x VTH / 15A (ii)
TD230
where CISS is the input capacitance of the power MOSFET1/2 and VTH, the threshold voltage of the MOSFET (typically 5V). This reconduction time can be extended with an external soft start capacitor CSS1/2 as shown in figure 1 CISS will therefore simply be replaced by CISS + CSS 1/2. Figure 1 : Dual Electronic Circuit Breaker Application Trace A represents the Gate-Source Voltage of the Power Mosfet (0 to 13,4V). Trace B represents the voltage across the Sense Resistor (68m) in direct relation with the current through it (0 to ~1A). Note that the first current peak which is due to an over current is limited only by the reaction time of the TD230. This off time is tied to the value of the external soft start capacitor CSS 1/2 by equation (iii) : * tOFF = RDSON x CSS (iii) While in current limitation mode, the NMOS1/2 dissipates low power due to the fact that the ON/OFF cycle time rate is very low. Note that the higher the value of CSS1/2 are, the more the NMOS1/2 will stay in linear mode during current limitation. Note that at Power ON, or in the case of live insertion, the inrush current is automatically limited thanks to the slow gate charge of the MOSFET which switches ON softly due to the time constant given in equation (ii). 2.2. Fault Time Limitation The repetitive switching off of the MOSFET will come to an end under two conditions : * either the fault has disappeared, and the current through the shunt resistors RS 1/2 has come back to its nominal value : the system keeps running normally. External line defaults (lightning, line breakage, etc...) are usual causes for such temporary over currents. * either the repetitive switching off has lasted over an externally adjustable time and the TD230 has definitively switched off the corresponding NMOS : the system waits to be reset. Equipment faults (component short circuit, over heat, etc ...) are usual causes for lasting over currents. This fault time supervision is done by the comparison of the output voltage to 75% of the nominal supply voltage. As soon as the output voltage is detected under 0.75xVcc(+/-), the corresponding external capacitors CTRIP1/2 is charged by a fixed current source IP/N2 - IP/N3 (3A). When the voltage across CTRIP1/2 reaches 1.20V, the corresponding NMOS is definitively switched off and the SHUTDOWN pin is active low.
RS 1
Vcc+
P Vcc R EF1
LBOO S T
1 2
LBOOS T GC1
16
NMos
15
CB OOS T S E NSP
CS S 1
to BOARD
CBO OS T
3 4 5
14 13 12 11 10
CS S 2 from BO ARD NMOS
C ONTRO L
O S C GND
INHIBIT
P M1
S HUTDOWN
CTRIP 1
6
CTRIP 2 GND
GND
S ENSN
7 8
Vcc-
P M2 NVcc
GC 2 R EF2
9
RS 2
If the fault (over current condition) still remains after the reconductionstate of the MOSFET1/2 has been reached, the current through NMOS1/2 will overpass the limitation given by equation (i), and the NMOS 1/2 will immediately be switched off again. Figure 2 shows the current limitation which is operated on every restart attempt. Figure 2 : TD230 as Current Limitor
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TD230
To avoid cumulative charging of the protection capacitors CTRIP 1/2 in case of successive overcurrent conditions, the capacitors CTRIP 1/2 are conFigure 3 : Fault Time Limitation
Rs e ns e
Figure 4 :
Step Up Converter External Components
Lboos t
Sense S tep Up
Cboos t
Driver TD230
MOS
The principle of this inductive step-up converter is to pump charges in the tank capacitor CBOOST following the equation (v) : stantly discharged by another fixed current source IP/N3 which value is a fourth of IP/N2 (1A). Trace 1 represents the CBOOST Voltage (0 to 5+13,4 = 18,4V) Trace 2 represents the CTRIP1 Voltage. The value of the capacitors CTRIP 1/2 should be chosen in relation with the required protection time as indicated in equation (iv) : * CTRIP1/2 = (IP/N2 - IP/N3) x tPROTECT1/2 / VSPN/3(iv) where tPROTECT 1/2 is the time defined by the user before a definitive resettable shutdown of MOSFET 1/2. Equation (iv) can be translated to : * CTRIP 1/2 = tPROTE CT 1/2 x 3A / 1.20V (iv) Note that the positive power supply disjonction leads to the negative power supply disjonction, whereas the opposite is not true. 2.3. Step-Up Converter To ensure proper voltage on the gate of the positive supply NMOS1 (VGS = 13.4V typ), the TD230 integrates a step-up converter which is to be boosted with two small low cost external components : an inductor LBOOST and a capacitor CBOOST, as shown in figure 4. Figure 5 : Internal Step Up Schematic
Lboos t
Cboos t Os c
Re gulation TD230
* V(CBOOST) = VCC+ + 13.4V typ (v) Charges are pumped by means of an oscillator commanded switch, and stored in the CBOOST tank capacitor through a diode as shown on figure 5. Wh en th e vo lt a ge across CBOOST reaches VCC++13.4V typ, the oscillator is stopped. This creates a ripple voltage with an amplitude of 0.2V. Note that the min and max values of V(CBOOST) comprised between VCC+ +10V and VCC+ +15V already take the ripple voltage into account.
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TD230
Proper operation of this step-up converter is guaranteed at as low as 2.7V with a rise time (0 to 90% of V(CBOOST)) in the range of 700s at 2.7V which Figure 6 : Step Up Converter Rise Time 2.4. Single Supply Breaker Application The TD230 is perfectly suited to fit in single supplied applications (ex 0-5V), and can drive only one power MOSFET used as high side power switch. Figure 7 shows how TD230 can be used as a single circuit breaker with the same performances. Figure 7 : Single Electronic Circuit Breaker Application
RS1
Vcc+
P Vcc R EF 1
LBOOS T
1 2
LBOOS T GC 1
16
NMos
15 14 13 12 11 10 9
CSS 1
to BOARD
CBOOS T
3 4 5
CBO OS T
S ENS P
OS C GND
INHIBIT
C ONTR OL
P M1
S HUTDOWN
CTRIP1
6
GND
S ENS N
is the worst case. At 5V, the rise time of V(Cboost) is 250s typ. The CBOOST voltage wave form at power ON under 5V supply voltage is shown on figure 6. Trace 1 represents the power supply voltage (0 to 5V). Trace 2 represents the CBOOST Voltage at power ON (0 to 5+13,4 = 18,4V). Table (a) summerizes the recommended values of the CBOOST and LBOOST to ensure optimized gate charge and low ripple voltage with their corresponding maximum current surge (IPK) and nominal consumption (I CC) of the TD230 for the most common power supply values. For each power supply value is also given the recommended value of a bypass capacitor (CBY) on the power supplies. Note that both CBOOST and LBOOST are available in surface mount packages. Table (a) : Recommended values for Cboost and Lboost
VCC+ V 2.7 5 10 12 14 18 Cboost nF 47 100 100 100 220 220 220 220 Lboost H 68 220 470 470 680 1000 Ipk mA 60 35 33 39 34 31 Vrip mV 190 100 120 220 100 150 150 200 Icc mA 5 2.5 2.2 2.2 2.4 2.7 Cby F >1 1 1 1 1 1
7
GND
P M2 NVcc
GC 2 R EF 2
8
In this case, the external components consist in : one boost inductor, one sense resistor, three capacitors, and one power MOSFET. 2.5. Typical Telecom Line Cards Protection Application One of the typical applications where the TD230 can display all its technical advantages is in an exchange Telecom Cards protection. Sometimes fifty cards or more are to be supplied with the same power supply (+/-5V, 1kW), and a decentralized protection is needed because one card may be faulty, but should not penalize the others with unadapted protection system. The risk of complete breakdown of the system must be eradicated. In this application the two above described over current causes (external line perturbation or internal component fault) are likely to happen. In the first case, the current limitation on each card will ensure undammagingon-board conditions, and in the second case, the faulty card will be disjoncted from the power supply until reset. Figure 8 shows a typical telecom application with decentralized protection. In this application, the positive power supply serves the logic control and analog signals whereas the negative power supply is dedicated to the analog.
9/15
TD230
Figure 8 : Decentralized Protection
Vcc+
P owe r S upply TD230 TD230 TD230 TD230
GND
BOARD1
BOARD2
BOARD3
BOARDN
Vcc-
Therefore, when a fault appears onthe positive rail, the definitive shutdown of the positive NMOS will lead to the shutdown of the negative NMOS, but when a fault appears on the negative rail, the definitive shutdown of the negativeNMOS will have no effect on the positive NMOS. Several possibilities are offered to reset the whole system when it has been led to definitive shutdown : * the card can be unplugged and plugged back (live insertion) * the INHIBIT pin can be set to active state during a short time (100s typ or more) in the case of remote control facilities 3. PERFORMANCES AND EVALUATION All the curves shown in this application note have been realized with the TD230 Evaluation Board. The external conditions and components were as listed hereafter : * Vcc+ = 5V * Vcc- = -5V * Suppliable output short circuit current = 5A * IC = TD230 * MOSFET 1 = BUZ71 * MOSFET 2 = BUZ71 * LBOOST = 220H * CBOOST = 100nF
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* CTRIP1 = 10F * CTRIP2 = 10F * RS1 = 68m * RS2 = 68m * CSS1 = 1nF * CSS2 = 1nF * Positive Bypass = 4.7F (plastic) * Negative Bypass = 4.7F (plastic) The evaluation board is available and allows to test the performances of the TD230. The layout and schematic of this evaluation board are given on figures 9A-9B-9C. 4. CAUTIONS For proper use of the TD230 as a reliable protection device, a few precautions must be taken : 1. Proper bypass capacitors must be connected as close as possible to the power pins of the TD230 (PVcc, NVcc, GND). Some recommended values are given in table (a). 2. The OSCGND pin must be tied to the GND pin externally (printed board) to ensure proper step-up converter reference. If not, the step-up converter will not start. 3. TheINHIBIT pin is a CMOS/TTL compatible input which should therefore not be left unconnected. The absolute maximum rating of this input is 7V. It should be tied to the TTL compatible output of an
TD230
Figure 9A : PCB (not to scale) Figure 9B : Silkscreen
Figure 9C : Schematic
eventual control block, or, if it should not be used, tied to the GND pin. 4. Th e SHUTDOWN pin is an open drain CMOS/TTL compatible output which should be tied to the TTL compatible input of an eventual control block. The absolute maximum rating of this output is 7V. In the case of a visual alarm, a LED is likely to be tied to the positive power supply which can be destructive for the Shutdown output if the power supply is over 7V. An easy way to eliminate this is
to add a 6V zener diode between the Shutdown output and the Ground as shown on figure 10. 5. The time constant of the protection mode (given by the charge of CTRIP1/2 capacitors) must be greater than the time constant of the restart attempts (given by the charge of the CSS 1/2 soft start capacitors). This condition can be described as follows : * VSP1/2 x CTRIP1/2 / IP/N2 > VTH1/2 x (CSS1/2+CISS1/2) / IP/N1
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TD230
Figure 10 : Visual Alarm-Shutdown
Vcc +
which, in most cases are, are not worrying. But in some very demanding applications, it is necessary to remove this noise. A good way to eliminate such peaks is to add a resistor connected in series with the inductance and an electrolytic capacitor between the common point of resistor and inductance, and ground of the Step-Up Converter as shown on figure 11. Figure 11 : Step Up Noise Reduction
Rs e ns e
TD230
S hutdown
R
where CISS1/2 , CSS1/2, VTH1/2 , IP/N1 are respectively the input capacitance, the soft start capacitor, the threshold voltage and the internal gate current sources of NMOS1/2 ; and where VSP1/2 , CTRIP1/2 , IP/N2 are respectively the voltage source, current source and external capacitor of the protection mode pins PM1/2. Considering the typical values of VSP1/2, IP/N2, IP/N1, and the fact that classical power MOSFETs have a threshold voltage around 5V, this condition can be translated to inequation (vi) : * CTRIP1/2 > 0.8 x (CSS1/2 + CISS ) (vi) If CISS = 1nF and CSS1/2 = 4.7nF, CTRIP1/2 should be superior to 4.56nF. Table (b) summerizes Protection Mode Time Constants corresponding to different CTRIP1/2 values. Table (b) : Protection Mode Time Constants
C TRIP1/2 22nF 220nF 2.2F 22F Time Constant Range for Protection Mode - Shutdown #10ms #100ms #1s #10s
C
Lboost
TD230 Cboost
The resistor's voltage drop will be due to the product of the average consumption current with the resistor's value and the inductive current peaks will be totally absorbed by the capacitor. With a 100 resistor, the voltage drop is negligible and the attenuationgood with a 4.7F as shown on figure 12. Figure 12 : Step Up Noise Reduction
5. ENHANCEMENTS The performances of TD230 are well adapted to most of the circuit breaking applications in many differents industry segments (Telecom, Automotive, Industrial, Computer etc...), but in the case of very demanding environment, or outstanding features, the few following advices may be helpful. 5.1. Step-Up Noise Reduction The inductive step-up converter inevitably generates current peaks in the output of the power switch
12/15
TD230
Trace A represents the ripple voltage on CBOOST (200mV width). Trace B represents the voltage perturbation due to the Step-Up converter on the output (source of the power Mosfet = Board power supply). Traces 1 and 2 represent the same, but improved thanks to the Step-Up Noise reduction RC. 5.2. Precision Enhancement If the system needs accurate current limitation in an environment subject to very wide temperature variations, a good way to compensate fluctuations due to temperature variations is to use a CTN as described in figure 13. 5.3. Temporisation In some cases, it can be useful to let short current peaks pass without reaction of the breaker, though these are of higher value than the fixedcurrent limit. This enables the Electronic Circuit Breaker to behave as a thermal disjonctor. This behaviour can easily be given by adding an RC constant as shown on figure 14. Figure 14 : Temporisation
Rse nse
Figure 13 : Wide Temperature Variations
Rs e ns e
R R CTN C
R
TD230
TD230
13/15
TD230
PACKAGE MECHANICAL DATA 16 PINS - PLASTIC DIP
Dimensions a1 B b b1 D E e e3 F i L Z
Min. 0.51 0.77
Millimeters Typ.
Max. 1.65
Min. 0.020 0.030
Inches Typ.
Max. 0.065
0.5 0.25 20 8.5 2.54 17.78 7.1 5.1 3.3 1.27
0.020 0.010 0.787 0.335 0.100 0.700 0.280 0.201 0.130 0.050
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TD230
PACKAGE MECHANICAL DATA 16 PINS - PLASTIC MICROPACKAGE (SO)
Dimensions A a1 a2 b b1 C c1 D E e e3 F G L M S
Min. 0.1 0.35 0.19
Millimeters Typ.
Max. 1.75 0.2 1.6 0.46 0.25 45 (typ.)
o
Min. 0.004 0.014 0.007
Inches Typ.
Max. 0.069 0.008 0.063 0.018 0.010
0.5 9.8 5.8 1.27 8.89 3.8 4.6 0.5 4.0 5.3 1.27 0.62 8 (max.)
o
0.020 10 6.2 0.386 0.228 0.050 0.350 0.150 0.181 0.020 0.157 0.209 0.050 0.024 0.394 0.244
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such info rmation nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publi cation are subject to change without notice. This publ ication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for useas critical components in life support devices or systems without express written approval of STMicroelectronics. (c) The ST logo is a trademark of STMicroelectronics (c) 1998 STMicroelectronics - Printed in Italy - All Rights Reserved STMicroelectronics GROUP OF COMPANIES Australia - Brazil - Canada - China - France - Germany - Italy - Japan - Korea - Malaysia - Malta - Mexico - Morocco The Netherlands - Singapore - Spain - Sweden - Switzerland - Taiwan - Thailand - United Kingdom - U.S.A. (c) http://www.st.com
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